The post presents an in-depth discussion regarding the construction details of a universal high power amplifier which can be modified or adjusted to suit any range within 60 watt, 120 watt, 170 watt or even 300 watt power output (RMS).
The circuit diagram in Fig. 2 tells about the highest power capability form of the amplifier, this offers 300 W into 4 ohms. Settings to moderate the power output will undoubtedly be talked over afterwards within the post.
The circuit relies upon the a couple of series hooked up MOSFETs, T15 and T16., actually being powered in anti-phase by a differential amplifier. Given that the input resistance of MOSFETs is of the level of 10 ohms, the drive electrical power really needs to be simply modest. The MOSFETs are as a result voltage- operated.
The driver stage is made up predominantly of T1 and T3 together with T12 and T13. Negative d.c. feedback through the output stage is supplied by R22 and negative a.c. feedback by R23----C3.
The a.c. voltage gain is roughly about 30 dB. The below cut-off frequency is determined by the values of C1 and C3. The working purpose of the first differential amplifier, T1, T2 is scheduled by the current streaming through T3.
The collector current of T5 ascertains the reference current for current mirror T3-T4. To make sure that that the referral current is constant, the base voltage of T5 is well controlled by diodes D4-D5.
The output of T1-T2 operates another differential amplifier, T12-T13, whose collector currents establish the gate potential for the output transistors. The measure of that potential would depend on the working position of T12-T13.
Current mirror T9 and T10 together with diodes D2-D5 hold the identical function as T3-T4 and D4-D5 in the first differential amplifier.
The significance of the referral current is characterized by the collector current of Tm, which often is scheduled by P2 in the emitter circuit of T11. This particular combination models the quiescent (bias) current without the presence of (an input signal.
Stabilization of quiescent current
The MOSFETs possess a positive temperature coefficient each time their drain current is nominal, guaranteeing that the quiescent (bias) current is simply maintained consistent by applicable compensation.
This is often made available from R17 over current mirror T9-T10, which includes a negative temperature coefficient. Once this resistor warms up, it begins drawing a relatively more substantial percentage of the reference current via T9.
This brings about a decrease in the collector current of T10 which, sequentially, brings about reduction in the gate-source voltage of the MOSFETs, which efficiently compensates the in- crease induced by the PTC of the MOSFETs.
The thermal period constant, that may be influenced by the thermal resistance of the heat sinks, decides the time needed for stabilization to be executed. The quiescent (bias) current fixed by P; is consistent within +/-30%.
The MOSFETs are shielded against overheating by thermistor R12 in the base circuit of T6. Any time a selected temperature is accomplished, the potential across the thermistor leads T7 to activate. Whenever that occurs, T8 derives the more substantial portion of the reference current by means of T9-T11, which successfully restricts the output power of the MOSFETs.
The heat tolerance is scheduled by Pl which is equal to a heat sink temperature of Short-circuit security In case the output is short-circuited in the occurrence of an input signal, the lowering in voltage across resistors R33 and R34 leads to T14 to be turned on.
This causes a drop of the current by way of T9/T10 and also, accordingly, of the collector currents of T12 and T13. The effective range of the MOSFETS is subsequently significantly constrained, making sure that the power dissipation is cut minimal.
Because the practicable drain current relies upon the drain-source voltage, more details is important for the proper setting up of the current controlling.
This details are offered by the voltage decrease across resistors R26 and R27 (positive and negative output signals respectively). When the load is less than 4 ohms, the base-emitter voltage of Tu is decreased to a level that contributes to the short-circuit current genuinely restricted to 3.3 A.
The MOSFET amplifier design is ideally built on the PCB presented in Fig. 3. Still, before construction is initiated,it needs to be determined which variation is preferred.
Fig. 2 as well as the components list of Fig. 3 are for the l60 watt variant. Adjustments for the 60 W, 80 W, and 120 W variations are presented in Table 2. As laid out in Fig. 4, the MOSFETs and NTCs are installed on a right-angled.
The pin connectivity are outlined in Fig. 5. The NTCs are screwed straight into M3- dimension, tapped (tapping drill = 2.5 mm), holes: make use of a lot of heatsink compound paste. Resistor Rza and Rai are soldered directly to the gates of the MOSFETs at the copper side of the PCB. Inductor L1 is wrapped on
R36: the wire should be effectively insulated, with ends pre-tinned soldered to the openings right next to those for R36. Capacitor C1 may perhaps be an electrolytic type, nevertheless an MKT version is advantageous. The surfaces of T1 and T2 ought to be pasted with each other with the intention that their body heat continues to be identical.
Remember the wire bridges. The power supply for the 160 watt model is shown in
Fig. 6: adjustments for the supplementary models are shown in Table 2. An artsist’s conception of its engineering is presented in
Fig. 7. As soon as the power unit is constructed, the open-circuit working voltages could possibly be checked.
The d.c. voltages needs to be not above +/- 55 V, else there is a risk that the MOSFETs would give up the goblin on initial power-on.
In case appropriate loads are obtainable, it will be, of course, advantageous that the source is examined under load restrictions. Once the power supply is realized to be Fine, the aluminium MOSFET setup is screwed directly to an appropriate heat sink.
Fig. 8 presents a pretty good feel of the height and width of the heat sinks and of the finalized assortment of a stereo model of the amplifier.
For simplicity, mainly the standing of the parts of the power source is demonstrated. The places where the heat sink and the aluminium MOSFET setup (and, probably, the backside panel of the amplifier enclosure) get together ought to be assigned an effective covering of heat conducting paste. Every of the two assemblies must be screwed to the incorporated heat sink with no less than 6 M4 (4 mm) sizing screws.
The electrical wiring must stick to the guide lines in Fig. 8 faithfully.
It is advisable to start with the supply traces (heavy gauge wire). Following, establish the ground connections (star-shaped) from the power device ground to the PCBs and the output ground.
Thereupon, create the cable connections between PCBs and loudspeaker terminals as well as those between the input sockets and the PCBs. The input ground should always be hooked up solely to the ground lead on the PCB - that's all!
Calibration and testing
Rather than fuses F1 and F2, attach 10ohm, 0.25 W, resistors in their location on the PCB. Preset P2 has to be fixed completely anticlockwise, although P1 is scheduled to the center of its rotation.
The loudspeaker terminals continue being open, as well as the input should be short-circuited. Power up the mains. Should there be any kind of short-circuits in the amplifier, the 10 ohm resistors will start fuming!
If that takes place, shut off right away, identify the problem, change the resistors, and turn on the power once more.
The minute everything looks proper, hook up a voltmeter (3 V or 6 V d.c. range) across one of the 10-ohm resistors. There has to be zero voltage across it.
If you find P1 is not flipped completely anticlockwise. The voltage ought to climb while P2 is steadily changed clockwise. Set P1 for a voltage of 2 V: the current in that case could be 200 mA, i.e.: 100 mA per MOSFET. Disconnect, and change the 10-ohm resistor by the fuses.
Turn on power yet again, and check the voltage between earth and amplifier output: this certainly will be not higher than +/-20 mV. The amplifier is after that prepared for intended functionality.
A concluding point. As previously explained, the changing over guideline of the overheating security circuit has to be allocated for approximately 72.5 °C.
This can easily be determined by heating the heat sink with, e.g., with a hair dryer and assessing its heat.
Yet somehow, this may not be exactly essential: P1 could also be allowed fixed at the middle of its dial. Its situation really should only be changed if the amplifier switches off too frequently.
However, its stance should on no account be faraway from the middle location.